LM4780 datasheet(17/24 Pages) NSC

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Application Information (Continued)

mined. Refer to the section, Determining the Correct Heat

Sink, for more information and detailed discussion of proper

heat sinking.

SINGLE-SUPPLY AMPLIFIER APPLICATION

The typical application of the LM4780 is a split supply am-

plifier. But as shown in Figure 4, the LM4780 can also be

used in a single power supply configuration. This involves

using some external components to create a half-supply bias

which is used as the reference for the inputs and outputs.

Thus, the signal will swing around half-supply much like it

swings around ground in a split-supply application. Along

with proper circuit biasing, a few other considerations must

be accounted for to take advantage of all of the LM4780

functions, like the mute function.

CLICKS AND POPS

In the typical application of the LM4780 as a split-supply

audio power amplifier, the IC exhibits excellent “click” and

“pop” performance when utilizing the mute mode. In addition,

the device employs Under-Voltage Protection, which elimi-

nates unwanted power-up and power-down transients. The

basis for these functions are a stable and constant half-

supply potential. In a split-supply application, ground is the

stable half-supply potential. But in a single-supply applica-

tion, the half-supply needs to charge up at the same rate as

the supply rail, V

CC. This makes the task of attaining a

clickless and popless turn-on more challenging. Any uneven

charging of the amplifier inputs will result in output clicks and

pops due to the differential input topology of the LM4780.

To achieve a transient free power-up and power-down, the

voltage seen at the input terminals should be ideally the

same. Such a signal will be common-mode in nature, and

will be rejected by the LM4780. In Figure 4, the resistor R

INP

serves to keep the inputs at the same potential by limiting the

voltage difference possible between the two nodes. This

should significantly reduce any type of turn-on pop, due to an

uneven charging of the amplifier inputs. This charging is

based on a specific application loading and thus, the system

designer may need to adjust these values for optimal perfor-

mance.

As shown in Figure 4, the resistors labeled R

BI help bias up

the LM4780 off the half-supply node at the emitter of the

2N3904. But due to the input and output coupling capacitors

in the circuit, along with the negative feedback, there are two

different values of R

BI, namely 10k

Ω and 200kΩ. These

resistors bring up the inputs at the same rate resulting in a

popless turn-on. Adjusting these resistors values slightly

may reduce pops resulting from power supplies that ramp

extremely quick or exhibit overshoot during system turn-on.

PROPER SELECTION OF EXTERNAL COMPONENTS

Proper selection of external components is required to meet

the design targets of an application. The choice of external

component values that will affect gain and low frequency

response are discussed below.

The gain of each amplifier is set by resistors R

f and Ri for the

non-inverting configuration shown in Figure 1. The gain is

found by Equation (6) below:

V =1+Rf /Ri (V/V)

(6)

For best noise performance, lower values of resistors are

used. A value of 1k

Ω is commonly used for R

i and then

setting the value of R

f for the desired gain. For the LM4780

the gain should be set no lower than 10V/V and no higher

than 50V/V. Gain settings below 10V/V may experience

instability and using the LM4780 for gains higher than 50V/V

will see an increase in noise and THD.

The combination of R

i with Ci (see Figure 1) creates a high

pass filter. The low frequency response is determined by

these two components. The -3dB point can be found from

Equation (7) shown below:

i =1/(2

πR

iCi) (Hz)

(7)

If an input coupling capacitor is used to block DC from the

inputs as shown in Figure 5, there will be another high pass

filter created with the combination of C

IN and RIN. When

using a input coupling capacitor R

IN is needed to set the DC

bias point on the amplifier’s input terminal. The resulting

-3dB frequency response due to the combination of C

IN and

IN can be found from Equation (8) shown below:

IN =1/(2

πR

INCIN) (Hz)

(8)

With large values of R

IN oscillations may be observed on the

outputs when the inputs are left floating. Decreasing the

value of R

IN or not letting the inputs float will remove the

oscillations. If the value of R

IN is decreased then the value of

IN will need to increase in order to maintain the same -3dB

frequency response.

HIGH PERFORMANCE CONSIDERATIONS

Using low cost electrolytic capacitors in the signal path such

as C

IN and Ci (see Figures1-5) will result in very good

performance. However, electrolytic capacitors are less linear

than other premium capacitors. Higher THD+N performance

may be obtained by using high quality polypropylene capaci-

tors in the signal path. A more cost effective solution may be

the use of smaller value premium capacitors in parallel with

the larger electrolytic capacitors. This will maintain signal

quality in the upper audio band where any degradation is

most noticeable while also coupling in the signals in the

lower audio band for good bass response.

Distortion is introduced as the audio signal approaches the

lower -3dB point, determined as discussed in the section

above. By using larger values of capacitors such that the

-3dB point is well outside of the audio band will reduce this

distortion and improve THD+N performance.

Increasing the value of the large supply bypass capacitors

will improve burst power output. The larger the supply by-

pass capacitors the higher the output pulse current without

supply droop increasing the peak output power. This will also

increase the headroom of the amplifier and reduce THD.

SIGNAL-TO-NOISE RATIO

In the measurement of the signal-to-noise ratio, misinterpre-

tations of the numbers actually measured are common. One

amplifier may sound much quieter than another, but due to

improper testing techniques, they appear equal in measure-

ments. This is often the case when comparing integrated

circuit designs to discrete amplifier designs. Discrete transis-

tor amps often “run out of gain” at high frequencies and

therefore have small bandwidths to noise as indicated below.

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